MC33067P datasheet(8/16 Pages) ONSEMI

No de pièce	MC33067P

Description	HIGH PERFORMANCE ZERO VOLTAGE SWITCH RESONANT MODE CONTROLLERS

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Fabricant	ONSEMI [ON Semiconductor]

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MC34067 MC33067

8

MOTOROLA ANALOG IC DEVICE DATA

The maximum oscillator frequency is set by the current

through resistor RVFO. The current required to discharge

COSC at the maximum oscillator frequency can be calculated

by Equation 2:

COSC

1.5C

(2)

OSC

I

1

ƒ

5.1 – 3.6

=

(max)

ƒ(max)

The discharge current through ROSC must also be known

and can be calculated by Equation 3:

ƒ

(min)

COSC

ROSC

1.5

ε

I

1

ƒ

5.1 – 3.6

=

(min)

R

ROSC

COSC

ROSC

=

ROSC

ε

1

(3)

–

OSC

Resistor RVFO can now be calculated by Equation 4:

(4)

R=

VFO

I(max)

IR

–

2.5 – VEAsat

OSC

One–Shot Timer

The One–Shot is designed to disable both outputs

simultaneously providing a deadtime before either output is

enabled. The One–Shot capacitor (CT) is charged

concurrently with the oscillator capacitor by transistor Q1, as

shown in Figure 14. The one–shot period begins when the

oscillator comparator turns off Q1, allowing CT to discharge.

The period ends when resistor RT discharges CT to the

threshold of the One–Shot comparator. The lower threshold

of the One–Shot is 3.6 V. By choosing CT, RT can by solved

by Equation 5:

5.1

3.6

(5)

CT

R

t OS

C

0.348

=

T

t OS

n

Errors in the threshold voltage and propagation delays

through the output drivers will affect the One–Shot period. To

guarantee accuracy, the output pulse of the control chip is

trimmed to within 5% of 250 ns with nominal values of RT and

CT.

The outputs of the Oscillator and One–Shot comparators

are OR’d together to produce the pulse tOS, which drives the

Flip–Flop and output drivers. The output pulse (tOS) is

initiated by the Oscillator and terminated by the One–Shot

comparator. With zero–voltage resonant mode converters,

the oscillator discharge time should never be set less than

the one–shot period.

Error Amplifier

A fully accessible high performance Error Amplifier is

provided for feedback control of the power supply system.

The Error Amplifier is internally compensated and features dc

open loop gain greater than 70 dB, input offset voltage of less

than 10 mV and a guaranteed minimum gain–bandwidth

product of 2.5 MHz. The input common mode range extends

from 1.5 V to 5.1 V, which includes the reference voltage.

Figure 15. Error Amplifier and Clamp

RVFO

Oscillator

Control Current

3.1V

Error Amp Output

Noninverting Input

Inverting Input

Error

Amp

IOSC

7

8

6

3

Error Amp

Charge

When the Error Amplifier output is coupled to the IOSC pin

by RVFO, as illustrated in Figure 15, it provides the Oscillator

Control Current, IOSC. The output swing of the Error Amplifier

is restricted by a clamp circuit to improve its transient

recovery time.

Output Section

The pulse(tOS), generated by the Oscillator and One–Shot

timer is gated to dual totem–pole output drives by the

Steering Flip–Flop shown in Figure 16. Positive transitions of

tOS toggle the Flip–Flop, which causes the pulses to alternate

between Output A and Output B. The flip–flop is reset by the

undervoltage lockout circuit during startup to guarantee that

the first pulse appears at Output A.

Figure 16. Steering Flip–Flop and Output Drivers

Output A

R

12

13

14

Output B

Power Ground

Q

T

Steering

Flip–Flop

±

Pwr

Gnd

VOE

Pwr

Gnd

The totem–pole output drivers are ideally suited for driving

power MOSFETs and are capable of sourcing and sinking

1.5 A. Rise and fall times are typically 20 ns when driving a

1.0 nF load. High source/sink capability in a totem–pole

driver normally increases the risk of high cross conduction

current during output transitions. The MC34067 utilizes a

unique design that virtually eliminates cross conduction, thus

controlling the chip power dissipation at high frequencies. A

separate power ground pin is provided to isolate the sensitive

analog circuitry from large transient currents.

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